Variable quantization adc for image sensors

ABSTRACT

An A/D converter suitable for use in a system in which the signal power of noise increases with the signal power of the signal, such as an imaging system, utilizes a variable quantization system for converting analog signals into digital signals. The variable quantization is controlled so that at low signal levels the quantization is similar or identical to conventional A/D converters, while the quantization level is increased at higher signal levels. Thus, higher resolution is provided at low signal levels while lower resolution is produced at high signal levels.

FIELD OF INVENTION

The present invention relates to an imaging system. More specifically,the present invention is directed to the use of variable quantizationwhile performing analog-to-digital (A/D) conversion in an imagingsystem.

BACKGROUND OF THE INVENTION

FIG. 1 is an illustration of a conventional imaging system 100. Thesystem 100 includes an N×M array 110 of pixels P. The system 100 may bemonochromatic or color. If the system 100 is a color system, the pixelsP in the array 110 would be sensitive to the primary colors of red,green, or blue, and would typically be arranged in a Bayer pattern(i.e., alternating rows are comprised of green/red and blue/greensensitive pixels in adjacent columns).

Each pixel P in the array 110 converts incident light into electricalenergy, which is output as an electrical signal. The signals from the Npixels forming a row in the array 110 are typically simultaneouslyoutput on respective column lines to respective sample-and-hold circuits120, which store the electrical signals. These signals are thenselected, one pixel at a time, for further processing by a driver 130,and then converted into a digital signal by an analog-to-digital (A/D)converter 140. The digital signals are further processed by a digitalprocessing section 150, and then stored by a storage device 160. Whenall the signals stored in the sample-and-hold circuits 120 have beenprocessed, another row of signals is output and stored in thesample-and-hold circuit 120 and the processing continues until each rowof the N×M array 110 has been processed. The above described processingmay be controlled by a control circuit 170. Alternatively, controlcircuit 170 may include a plurality of control circuits.

An ideal pixel would output an analog pixel signal with no noisecomponent in a manner consistent with the amount of incident light uponthe pixel. In order to achieve a high fidelity image, a conventionalhigh resolution (e.g., 12 to 14 bits) A/D converter is typically used toconvert the pixel signal into a digital signal. However, one drawbackassociated with conventional high resolution A/D converters is that theyrequire a relatively long time to perform each A/D conversion. Forexample, converter 140 might be based on a “ramp” design, which requiresmany processing steps in the A/D conversion.

Now referring to FIGS. 2A and 2B, it can be seen that a ramp type A/Dconverter 200 operates by sampling and holding the input signal (Vs)over a sampling period (ts) comprised of a plurality of clock cycles (1tc, 2 tc, . . . , 8 tc). The A/D converter 200 is initialized when thestart pulse control 201 generates the logical high portion of a startpulse. This resets the value stored in counter 204, resets the state ofthe ramp generator 205, and causes the AND gate 203 to output a lowlogical state. Thereafter, during each clock cycle (1 tc-8 tc), thevalue of the counter 204 is incremented by one, and the state of theramp generator 205 is changed to cause the ramp generator 205 togenerate a new reference signal Vr. A comparator 206 compares thereference signal Vr against the input signal Vs. If the magnitude of thereference signal Vr does not exceed that of the input signal Vs, thecomparator 206 outputs a logical high state to the AND gate 203, whichwhen combined with a clock pulse generated by clock 202 and the lowlogical state portion of the start signal, toggles the clock inputs ofcounter 204 and ramp generator 205.

Each time counter 204 is toggled, it increases is value by one. Thus, oneach successive cycle, the ramp generator 205 generates a highermagnitude reference voltage Vr until the magnitude of the referencevoltage Vr exceeds the magnitude of the sample signal. Thereafter, thecomparator outputs a low logical state to AND gate 203, causing the ANDgate 203 to continually output a low logical state, thereby freezing thecounter value. When enough clock cycles have elapsed to constitute anentire sample period, the counter value is equal to the digitallyconverted value. Once the counter value has been read out, the startpulse control can generate a new start pulse to cause the A/D converter200 to being the conversion process again.

It should be apparent from the discussion above with respect to FIGS.2A-2B that an I-bit ramp type A/D converter requires a minimum samplingtime equal to 2^(I) clock cycles in order to permit sufficient time tocompare the maximum ramp value with the input signal. Thus, thethroughput of an imaging system 100 (FIG. 1) is at least partiallylimited by the speed of the A/D converter 140, especially when highresolution (e.g., I=12 or more) A/D conversion is employed. Accordingly,there is a need for a method and mechanism for performing highresolution A/D conversion at a faster rate.

SUMMARY OF THE INVENTION

Embodiments of the present invention provide an A/D converter, andmethod of operation of same, which utilizes a variable quantizationsystem for converting analog signals into digital signals. The variablequantization is controlled so that at low signal levels the quantizationis similar or identical to conventional A/D converters, while thequantization level is increased at higher signal levels. Thus, higherresolution is provided at low signal levels while lower resolution isproduced at high signal levels.

BRIEF DESCRIPTION OF THE DRAWINGS

The foregoing and other advantages and features of the invention willbecome more apparent from the detailed description of exemplaryembodiments of the invention given below with reference to theaccompanying drawings, in which:

FIG. 1 is a block diagram of a conventional imaging system;

FIG. 2A is a diagram illustrating the operation of a conventional ramptype A/D converter;

FIG. 2B is a block diagram of a conventional ramp type A/D converter;

FIG. 3 is a graph illustrating the relative levels of photo and noisesignals from a pixel;

FIGS. 4A-4C are graphs illustrating different transfer functions betweenan input analog voltage and an output digital word;

FIG. 5A is a block diagram of a circuit for replacing counter 204 inFIG. 2B;

FIG. 5B is a block diagram of a ramp generator having multiple capacitorbanks;

FIG. 5C is a block diagram of a A/D converter in accordance with oneembodiment of the present invention; and

FIG. 6 is a block diagram of a processor based system utilizing thepresent invention.

DETAILED DESCRIPTION OF THE INVENTION

Now referring to the drawings, where like reference numerals designatelike elements, there is shown in FIG. 3 a graph illustrating therelationship between photo signal level (i.e., pixel signal level) andnoise level. As shown in FIG. 3, the noise level is approximately thesquare root of the photo signal level. Thus, as the photo or pixelsignal level increases, so does the noise level, however, the gapbetween the pixel signal level and the noise level also increases.

In the present invention, a variable quantization A/D converter isutilized to implement an alternate transfer function between an inputanalog voltage and a output digital word, in order to take advantage ofthe above illustrated relationship. Referring now to FIG. 4A, the lineartransfer function between an input analog voltage IN and a outputdigital word OUT from a conventional A/D converter is illustrated. Asshown in FIG. 4A, in a conventional A/D converter, the output digitalword varies linearly with the input analog signal. The slope and thestep increments of the transfer function in FIG. 4A remains unchangedbetween low and high levels of the input signal IN, indicating that thesame precision is retained in the conversion across all input signallevels.

As illustrated in FIG. 3, in an imaging system, at low photo signallevels, noise levels are low, thereby permitting high precision A/Dconversion. However, at high photo signal levels, noise levels alsoincrease, thereby making high precision A/D conversion increasinglyproblematic as photo signal levels increase. Thus, as is discussedbelow, FIGS. 4B and 4C illustrate alternate transfer functions of aninput analog voltage and an output digital word that would be moresuitable for use in imaging systems than the transfer functionillustrated in FIG. 4A.

Now referring to FIG. 4B, it can be seen that the illustrated transferfunction behaves identically to the transfer function of FIG. 4A at lowinput signals IN levels. At increasing levels of the input signal IN,however, the increment between conversion steps (in both the IN and OUTaxis) are also increased. That is, while transfer functions of FIGS. 4Aand 4B span the same input IN and output OUT ranges, in the transferfunction of FIG. 4B, at higher levels of the input signal, increasinglevels of the input signal IN are mapped to the same output signal valueand a lesser number of output signal values OUT are valid outputs.

The transfer function illustrated in FIG. 4C also behaves identically tothe transfer function of FIG. 4A at low input signal IN levels. Atincreasing levels of the input signal IN, however, the increment inconversion steps for the IN axis is increased while the increment inconversion steps for the OUT axis is unchanged. That is, in comparisonto the transfer function of FIG. 4A, the transfer function of FIG. 4Cspans the identical range of IN values while spanning a lesser range ofOUT values. Further, at increasing levels of the input signal IN, anincreasing number of levels of the input signal are mapped to the sameOUT value. Although the same number of OUT values are valid outputs forthe transfer functions shown in FIGS. 4B and 4C, the range of OUT valuesfor the transfer function of FIG. 4B spans the same range as that ofFIG. 4A while the range of OUT values for the transfer function of FIG.4C spans a lesser range than that of FIGS. 4A and 4B. In one exemplaryembodiment, the transfer function illustrated in FIG. 4A would be a12-bit linear transfer function, while the transfer functions of FIGS.4B and 4C would be 10-bit transfer functions (i.e., the number of validoutput signals OUT has been reduced by a factor of 4 over the transferfunction of FIG. 4A).

The transfer function of FIG. 4B is generally known as a linear modetransfer function while the transfer function of FIG. 4C is generallyknown as a compressed mode transfer function. A variable quantizationA/D converter in accordance with the principles of the present inventionmay be constructed using either the linear or compressed mode transferfunctions by using a modified version of the circuit of FIG. 2B.Essentially, the circuit of FIG. 2B can be used, except that the rampgenerator 205 and the counter 204 will be replaced with different rampgenerators and counters.

More specifically, to implement the linear mode transfer function, boththe ramp generator 205 and the counter 204 are modified so that atincreasingly high signal levels both circuits ramp up in identical stepsconsistent with the transfer function as shown in FIG. 4B. That is, whenthe ramp voltage begins to increment in double steps, the counter mustalso increment in double steps. As the ramp voltage increments increasesfurther, so must the counter. To implement the compressed mode transferfunction, the original counter 204 is utilized while the ramp generator205 is modified so that at increasingly high signal levels the rampgenerator ramps up in steps consistent with the transfer function asshown in FIG. 4C. Referring now to FIGS. 5A and 5B, it can be seen thatthe linear mode transfer function embodiment of the invention may beimplemented by replacing the counter 204 in FIG. 2B with the circuit204′ of FIG. 5A. Furthermore, implementing either the linear mode or thecompressed mode transfer function of the present invention also requiresreplacing the ramp generator 205 of FIG. 2B with ramp generator 205′ ofFIG. 5B.

In the new counter circuit 204′ illustrated in FIG. 5A, the clock andreset signals previously supplied to counter 204 in FIG. 2B are routedto a controller 501, which reads successive values from a ROM 512. TheROM 512 contains the output values OUT for the transfer function of FIG.4B or FIG. 4C. The controller 501 loads each successive output valuefrom the ROM 512 into the register 502 as the clock signal isincremented. When the reset signal is pulsed, the controller is set toread the next output value from the ROM 512 starting at the ROM's firstaddress.

In FIG. 5B, the new ramp generator 205′ includes multiple capacitorbanks 520 a, 520 b, 520 c. Each capacitor bank 520 a, 520 b, 520 cdiffers only in that the capacitance of each capacitor in a particularbank is different from those of the other banks. For example, in oneembodiment, the capacitance of each capacitor C₁ is one quarter that ofthe capacitance of each capacitor C₃, and the capacitance of eachcapacitor C₂ is one half of that of the capacitance of each capacitorC₃. The outputs from each capacitor bank 520 a, 520 b, 520 c are coupledtogether to form a single output from the ramp generator 205′. The useof different capacitor banks with different capacitances permits the useof fewer capacitors to span the reduced number of required outputvoltages.

The clock and reset signals previously supplied to the single shiftregister 210 in FIG. 2C are now instead supplied to a controller 511.The controller 511 is coupled to a ROM 512′ which stores code wordscorresponding to the transfer function of FIG. 4B. More specifically,the code words are used to instruct the controller 511 to increment oneor more of the clock signals and/or to reset one or more of the shiftregisters 210, in the plurality of capacitor banks 520 a, 520 b, 520 cin order to provide a ramp voltage consistent with the desired transferfunction.

FIG. 5C is a block diagram of an A/D converter 200′ in accordance withone embodiment of the present invention. The A/D converter 200′ includesmany of the same parts as the conventional A/D converter 200 (FIG. 2),but respectively substitutes the above described ramp generator 205′ andcounter circuit 204′ in place of the conventional ramp generator 205 andcounter 204. Thus, the A/D converter 200′ can implement the linear orcompressed mode transfer functions as described above.

FIG. 6 is an illustration of a processor based system 600 incorporatinga processor 601, a memory 602, at least one peripheral device 603, andan imaging system 604, each coupled to a bus 610. The imaging system 604incorporates at least one A/D converter 200′ (FIG. 5C) of the invention.

The present invention therefore provides for the use of variablequantization A/D conversion in an imaging system. According to oneembodiment, a variable quantization A/D converter provides the variablelevels of quantization, and is operated such that at higher levels ofthe input signal, the degree of quantization is increased. Thisembodiment provides for faster A/D conversion, for example, in a ramptype A/D converter. In accordance with another aspect of the invention,a ramp generator includes a plurality of capacitor banks, with eachcapacitor bank utilizing capacitors of varying values. In oneembodiment, the capacitance of the capacitors of each capacitor bank arerelated as powers of 2 to one of the capacitor banks. The choice betweenthe transfer functions illustrated in FIGS. 4B and 4C is left to thedesigner of the imaging system. However, it should be recognized thatthe invention may also be practiced in a variety of other manners. Forexample, the invention may also be practiced by a combination of alinear and non-linear A/D converters. Alternatively, the invention mayalso be practiced by passing the output of a linear A/D converter to anon-linear processing circuit which performs non-linear signalmapping/compression. Such a processing circuit might, for example, mapor compress output of a linear A/D converter by using a look-up table tomap input values to output values.

While the invention has been described in detail in connection with theexemplary embodiment, it should be understood that the invention is notlimited to the above disclosed embodiment. Rather, the invention can bemodified to incorporate any number of variations, alternations,substitutions, or equivalent arrangements not heretofore described, butwhich are commensurate with the spirit and scope of the invention.Accordingly, the invention is not limited by the foregoing descriptionor drawings, but is only limited by the scope of the appended claims.

1-47. (canceled)
 48. A method for generating a sequence of referencevoltages, comprising: receiving a sequence of clock signals; and on eachclock signal: reading a plurality of control words from a memory, eachone of the plurality of control words corresponding to a different oneof a plurality of capacitor banks; sending or not sending a control andreset signal to each of the plurality of capacitor banks based on thecontent of a corresponding control word; controlling a plurality ofswitches at each of the plurality of capacitor banks, each of theswitches being associated with a capacitor and controlling one of aplurality of voltage sources coupled to one plate of the capacitor, toproduce a bank output voltage; and summing each bank output voltage toproduce a master output voltage.
 49. An imaging system comprising: apixel array; and an analog to digital (A/D) converter circuit configuredto receive analog signals from the pixel array and to convert the analogsignals to digital signals with a variable-bit level of quantization,the A/D converter circuit comprising: a linear A/D converter configuredto produce intermediate values from the analog signals, the linear A/Dconverter comprising a ramp generator; and a processing circuitconfigured to remap the intermediate values produced by the linear A/Dconverter using a mapping table.
 50. A method for converting an analogsignal to a digital word, comprising: measuring a magnitude of theanalog signal; mapping the magnitude to a digital word with a first andsecond transfer function only, wherein: if the magnitude is less than apredetermined threshold, mapping the magnitude to the digital wordexclusively with the first transfer function, if the magnitude is atleast equal to the predetermined threshold, mapping the magnitude to thedigital word exclusively with the second transfer function, the firsttransfer function is not included in the second transfer function, andthe second transfer function is not included in the first transferfunction.
 51. The method of claim 50, wherein the first transferfunction maps each magnitude below the predetermined threshold to acorresponding reference signal in a linear manner.
 52. The method ofclaim 51, wherein the second transfer function maps each magnitude atleast equal to the predetermined threshold to corresponding referencesignals in a logarithmic manner.
 53. A method for converting an analogsignal to a digital word, comprising: measuring a magnitude of theanalog signal; if the magnitude is not greater than a predeterminedthreshold, mapping the magnitude to a digital word in accordance with afirst transfer function; and if the magnitude is at least equal to thepredetermined threshold, mapping the magnitude to the digital word inaccordance with a second transfer function, wherein: the first transferfunction maps each magnitude below the predetermined threshold to acorresponding reference signal in a linear manner, and the secondtransfer function maps a set of non-sequential and increasing magnitudeseach at least equal to the predetermined threshold to correspondingreference signals in a linear manner.
 54. A method for operating animaging system, comprising: receiving an analog pixel signal from apixel; converting the analog pixel signal into a digital word, whereinthe converting comprises: measuring a magnitude of the analog signal;mapping the magnitude to a digital word with a first and second transferfunction only, wherein: if the magnitude is less than a predeterminedthreshold, mapping the magnitude to the digital word exclusively withthe first transfer function, if the magnitude is at least equal to thepredetermined threshold, mapping the magnitude to the digital wordexclusively with the second transfer function, the first transferfunction is not included in the second transfer function, and the secondtransfer function is not included in the first transfer function. 55.The method of claim 54, wherein the first transfer function maps eachmagnitude below the predetermined threshold to a corresponding referencesignal in a linear manner.
 56. The method of claim 55, wherein thesecond transfer function maps each magnitude at least equal to thepredetermined threshold to corresponding reference signals in alogarithmic manner.
 57. A method for operating an imaging system,comprising: receiving an analog pixel signal from a pixel; convertingthe analog pixel signal into a digital word, wherein the convertingcomprises: measuring a magnitude of the analog signal; if the magnitudeis not greater than a predetermined threshold, mapping the magnitude toa digital word in accordance with a first transfer function; and if themagnitude is at least equal to the predetermined threshold, mapping themagnitude to the digital word in accordance with a second transferfunction, wherein: the first transfer function maps each magnitude belowthe predetermined threshold to a corresponding reference signal in alinear manner, and the second transfer function maps a set ofnon-sequential and increasing magnitudes each at least equal to thepredetermined threshold to corresponding reference signals in a linearmanner.